Electrical load driving apparatus

ABSTRACT

The electrical load driving apparatus includes means for alternately lowering the gate voltages of two current supply transistors connected in parallel to each other at regular time intervals, a current being supplied to an electrical load through drain-source paths of both the current supply transistors, and means for detecting wire breakage in two current supply wires in which the current supply transistors are interposed respectively at portions near the electrical load with respect to the current supply transistors based on the drain-source voltages of the current supply transistors.

This application claims priority to Japanese Patent Application No.2010-290903 filed on Dec. 27, 2010, the entire contents of which arehereby incorporated by reference.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to an electrical load driving apparatusfor supplying a current to an electrical load through a plurality oftransistors.

2. Description of Related Art

Japanese Patent Application Laid-open number 2003-158447 discloses suchan electrical load driving apparatus having a structure in which aplurality of power supply wires are connected in parallel, oneconnection node of the power supply wires being connected to one end ofan electrical load which is connected to one of the high voltage sideand the low voltage side of a power source, the other node beingconnected to the other of the high voltage side and the low voltage sideof the power source, and each of the power supply wires including acurrent supply transistor interposed therein. Accordingly, in thisstructure, a plurality of the current supply transistors are connectedin parallel with one another, and connected in series to the electricalload.

In this apparatus, the current supply transistors are turned on during acurrent supply period in which the electrical load should becontinuously supplied with a current.

According to the above structure, it is possible to maintain supply of acurrent to the electrical load even if one of the current supply wiresis broken.

Further, the above electrical load driving apparatus is configured togenerate sole-on periods within the current supply period, only acorresponding one of the current supply transistors being turned onduring each sole-on period, and to monitor the voltage at the outputterminals of the current supply transistors connected in parallel withone another during the sole-on period to determine whether or not thecurrent supply transistor to be turned on within the sole-on period hasan open failure in which the transistor is fixed to the off state.

This configuration makes it possible to detect an open failure of eachcurrent supply transistor, and also to detect a wire breakage of eachcurrent supply wire as an open failure of the current supply transistorregardless whether the wire breakage occurs at a portion on the nearside of the current supply transistor, or at a portion on the far sideof the current supply transistor with respect to the electrical load.

However, the above conventional electrical load driving apparatus has adisadvantage in reliability, because the sole-on period is generatedwithin the current supply period.

More specifically, in a case where the electrical load is not a loadthat should be driven only a short period in response to a certainevent, but a load that should be drive continuously (for example a relayfor relaying power to an ignition system of a vehicle), since thefailure detection is performed by turning on one of the current supplytransistors during each sole-on period all the while the vehicle isrunning, the current supply transistors may degrade quickly.

In addition, if one of the current supply transistors has an openfailure or if one of the current supply wires is broken, current supplyto the electrical load is interrupted during each corresponding sole-onperiod.

SUMMARY

An exemplary embodiment provides an electrical load driving apparatuscomprising:

a plurality of current supply wires connected in parallel with oneanother, each of the current supply wires being connected to one of ahigh voltage terminal and a low voltage terminal of a power source atone end thereof, and being connected to one end of an electrical load atthe other end thereof, the other end of the electrical load beingelectrically connected with the other of the high voltage terminal andthe low voltage terminal of the power source;

a plurality of current supply transistors having one control terminaland two output terminals, each of the current supply transistors beinginterposed in a corresponding one of the current supply wires at the twooutput terminals thereof to supply a current to the electrical load whenbeing turned on during a current supply period in which the electricalload should be supplied with the current continuously;

a check period generating section that successively generates a firstcheck period within the current supply period, a specific one of thecurrent supply transistors being turned on in a completely turn-on statewhere a voltage difference between the two output terminals thereof islower than or equal to a predetermined value so that the specificcurrent supply transistor is turned on completely, the current supplytransistors other than the specific current supply transistor beingturned on in a low current supply performance state where a voltagedifference between the two output terminals thereof is higher than thepredetermined value so that the current supply transistors other thanthe specific current supply transistor are turned on incompletely, thespecific current supply transistor being selected from among all of thecurrent supply transistors in sequence within the current supply period;and

a wire breakage determining means configured to determine, upondetecting that a voltage variation in a voltage of one of the two outputterminals which is located on the side near the electrical load withrespect to the current supply transistors between any one of the currentsupply transistors and any other one of the current supply transistorsexceeds a predetermined threshold, that a wire breakage is present in aportion of one of the current supply wires on the side near theelectrical load with respect to the current supply transistors.

According to the exemplary embodiment, there is provided an electricalload driving apparatus including a plurality of current supplytransistors connected in parallel with one another to supply a currentto an electrical load, and capable of detecting wire breakage in aplurality of current supply wires in each of which a corresponding oneof the current supply transistors is interposed without placing a largecurrent burden on the current supply transistors and withoutinterrupting current supply to the electrical load.

Other advantages and features of the invention will become apparent fromthe following description including the drawings and claims.

BRIEF DESCRIPTION OF THE DRAWINGS

In the accompanying drawings:

FIG. 1 is a diagram showing the structure of an ECU as an electricalload driving apparatus according to a first embodiment of the invention;

FIG. 2 is a diagram showing the structure of a drive circuit included inthe ECU shown in FIG. 1;

FIG. 3 is a time chart for explaining the operation of the ECU shown inFIG. 1;

FIG. 4 is a flowchart showing a load side wire breakage detectionprocess performed by a failure detecting section included in the ECUshown in FIG. 1;

FIG. 5 is a flowchart showing a voltage variation control inhibitionprocess performed by a microcomputer included in the ECU shown in FIG.1;

FIG. 6 is a time chart showing the operation of an ECU as an electricalload driving apparatus according to a second embodiment of theinvention;

FIG. 7 is a time chart showing an example of output patterns of voltagevariation command signals SC1 and SC2 in the second embodiment; and

FIG. 8 is a flowchart showing an opposite load side wire breakagedetection process performed by a failure detecting section included inthe ECU shown in FIG. 6.

PREFERRED EMBODIMENTS OF THE INVENTION First Embodiment

FIG. 1 is a diagram showing the structure of an ECU 11 as an electricalload driving apparatus according to a first embodiment of the invention.

The ECU 11 is mounted on a vehicle to turn on and off a relay 13 mountedon the vehicle by passing a current to a coil 13 a of the relay 13. Whenthe relay 13 is turned on, a battery voltage VB of a battery 15 issupplied to various vehicle-mounted units and devices related to theignition system of the vehicle as a power supply voltage. Morespecifically, the ECU 11 turns on the relay 13 when a vehicle driveroperates the ignition switch of the vehicle to supply the batteryvoltage VB to the various vehicle-mounted units and devices, and turnsoff the relay 13 when the vehicle driver turns off the ignition switchon condition that a predetermined power supply stop condition issatisfied.

In this embodiment, the relay coil 13 a of the relay 13 is high sidedriven by the ECU 11. Accordingly, one end of the relay coil 13 a isconnected to the negative terminal of the battery 15 through a groundline of the vehicle outside the ECU 11.

The ECU 11 includes a terminal 17 connected to the other end of therelay coil 13 a opposite to the ground line, a terminal 19 connected tothe positive terminal (high voltage terminal) of the battery 15, and twocurrent supply transistors Tr1 and Tr2 each of which passes a current tothe relay coil 13 a when turned on. In this embodiment, the transistorsTr1 and Tr2 are N-channel MOSFETs.

The two current supply transistors Tr1 and Tr2 are connected in parallelto each other, and connected in series to the relay coil 13 a.

More specifically, the ECU 11 includes current supply wires L1 and L2connected in parallel to each other, each of which is connected to theterminal 17 at one end thereof and connected to the terminal 19 at theother end thereof. The current supply wire L1 is interposed by thecurrent supply transistor Tr1 such that the drain terminal is on theupstream side (on the terminal 19 side) and the source terminal is onthe downstream side. The current supply wire L2 is interposed by thecurrent supply transistor Tr2 such that the drain terminal is on theupstream side (on the terminal 19 side) and the source terminal is onthe downstream side.

Hence, the current supply wire L1 includes a load side portion LS1located on the near side of the relay coil 13 a as an electrical loadand connecting the source terminal of the current supply transistor Tr1to the terminal 17 of the ECU 11, and an opposite load side portion LD1located on the far side of the relay coil 13 a and connecting the drainterminal of the current supply transistor Tr1 to the terminal 19 of theECU 11. Likewise, the current supply wire L2 includes a load sideportion LS2 located on the near side of the relay coil 13 a andconnecting the source terminal of the current supply transistor Tr2 tothe terminal 17 of the ECU 11, and an opposite load side portion LD2located on the far side of the relay coil 13 a and connecting the drainterminal of the current supply transistor Tr2 to the terminal 19 of theECU 11.

The ECU 11 includes a microcomputer 20 which controls current supply tothe relay coil 13 a, a drive circuit 21 which turns on and off thecurrent supply transistor Tr1 in accordance with an on/off commandsignal SD1 outputted from the microcomputer 20, and a drive circuit 22which turns on and off the current supply transistor Tr2 in accordancewith an on/off command signal SD2 outputted from the microcomputer 20.The ECU 11 further includes a voltage variation control section 31 and afailure detecting section 32 for detecting wire breakage of the currentsupply wires L1 and L2.

The drive circuit 21 turns on the current supply transistor Tr1 byapplying a drive voltage to the gate terminal as a control terminal ofthe current supply transistor Tr1 when the on/off command signal SD1 isat the active level (high level in this embodiment). The drive circuit22 turns on the current supply transistor Tr2 by applying a drivevoltage to the gate terminal as a control terminal of the current supplytransistor Tr2 when the on/off command signal SD2 is at the active level(high level).

Upon detecting that the vehicle driver turns on the ignition switch, themicrocomputer 20 brings the on/off command signals SD1 and SD2respectively supplied to the drive circuits 21 and 22 to the high levelat the same time as shown in FIG. 3. Thereafter, upon detecting that thevehicle driver turns off the ignition switch, the microcomputer 20brings the on/off command signals SD1 and SD2 to the low level oncondition that a predetermined current supply stop condition issatisfied.

As explained above, the microcomputer 20 sets both the on/off commandsignals SD1 and SD2 at the high level to turn on both the current supplytransistors Tr1 and Tr2 during a current supply period in which therelay coil 13 a should be energized continuously, so that a current issupplied to the relay coil 13 a through the two current supplytransistors Tr1 and Tr2.

Although not shown in FIG. 1, the microcomputer 20 is inputted with asignal indicating that the vehicle driver turns on or off the ignitionswitch to detect whether the ignition switch is on or off. The currentsupply stop condition may be that a current supply stop permissionsignal transmitted on a signal line (not shown) is received from avehicle-mounted unit supplied with electric power through the relay 13.

Next, the operations of the drive circuits 21 and 22 are explained indetail. Here, since the drive circuits 21 and 22 have the samestructure, only the operation of the drive circuit 21 is explained.

As shown in FIG. 2, the drive circuit 21 includes a voltage step-upcircuit 25 for stepping up the battery voltage VB (which is 12 to 14 Vin this embodiment) being supplied to the ECU 11 through the terminal19, a diode 26 whose anode is applied with the battery voltage VB, aswitching element 27 as an analog switch connected between the voltageoutput terminal of the voltage step-up circuit 25 and the gate terminalof the current supply transistor Tr1, and a switching element 28 as ananalog switch connected between the cathode of the diode 26 and the gateterminal of the current supply transistor Tr1.

The switching elements 27 and 28 turn on when the on/off command signalSD1 outputted from the microcomputer 20 is at the high level to connectthe voltage output terminal of the voltage step-up circuit 25 and thecathode of the diode 26 to the gate terminal of the current supplytransistor Tr1, and turn off when the on/off command signal SD1outputted from the microcomputer 20 is at the low level to disconnectthe voltage output terminal of the voltage step-up circuit 25 and thecathode of the diode 26 from the gate terminal of the current supplytransistor Tr1.

The voltage step-up circuit 25 includes a voltage generating section 25a which generates a voltage higher than the battery voltage VB bystepping up the battery voltage VB and outputs the generated voltagefrom the voltage output terminal of the voltage step-up circuit 25, anda voltage control section 25 b which adjusts the voltage generated bythe voltage generating section 25 a.

The voltage control section 25 b adjusts the voltage generated by thevoltage generating section 25 a to a voltage (20 V, for example) highenough to turn on the current supply transistor Tr1 completely in itssaturation state by being applied to the gate terminal of the currentsupply transistor Tr1, when a later explained voltage variation commandsignal SC1 outputted from the voltage variation control section 31 is atthe non-active level (low level in this embodiment). This voltage isreferred to as “completely turning-on voltage” hereinafter.

On the other hand, the voltage control section 25 b adjusts the voltagegenerated by the voltage generating section 25 a to a specific voltagehigher than the battery voltage VB and lower than the completelyturning-on voltage. This specific voltage is a voltage for turning onthe current supply transistor Tr1 by being applied to the gate terminalof the current supply transistor Tr1 in a state where the current supplyperformance of the current supply transistor is lower than that whenbeing applied with the completely turning-on voltage. This specificvoltage (15 V, for example) makes the drain-source voltage of thecurrent supply transistor Tr1 at a certain voltage higher than that whenthe current supply transistor Tr1 is in the completely-on state. Thisspecific voltage is referred to as “current supply performance loweringvoltage” hereinafter.

Hence, as shown in FIG. 3, when the on/off command signal SD1 outputtedfrom the microcomputer 20 is at the high level, and the voltagevariation command signal SC1 is at the low level, the gate voltage VG1of the current supply transistor Tr1 is at the completely turning-onvoltage (20 V) generated by the voltage step-up circuit 25, and as aresult, the drain-source voltage of the current supply transistor Tr1become 0.5 V, for example. Accordingly, when the on/off command signalSD1 outputted from the microcomputer 20 is at the high level, and thevoltage variation command signal SC1 is at the low level, the sourcevoltage VS1 as the output voltage of the current supply transistor TR1becomes 13.5 V which is lower than the drain voltage VD1 equal to thebattery voltage VB (14 V) by 0.5 V.

On the other hand, when the on/off command signal SD1 outputted from themicrocomputer 20 is at the high level, and the voltage variation commandsignal SC1 is at the high level, the gate voltage VG1 of the currentsupply transistor Tr1 is at the current supply performance loweringvoltage (15 V), and as a result, the current supply transistor Tr1 turnson in the low current supply performance state where the drain-sourcevoltage is at a value lower than that when the current supply transistorTr1 is in the completely on state. Hence, as shown in FIG. 3, when boththe on/off command signal SD1 and the voltage variation command signalSC1 are at the high level, the source voltage VS1 of the current supplytransistor becomes 13.0 V which is lower than the drain voltage VD1equal to the battery voltage VB (14 V) by 1.0 V.

The above descriptions of the structure and operation of the drivecircuit 21 can be applied to the drive circuit 22 except that the on/offcommand signal SD1 outputted from the microcomputer 20 is replaced bythe on/off command signal SD2, the voltage variation command signal SC1outputted from the voltage variation control section 31 is replaced bythe voltage variation command signal SC2, and the current supplytransistor Tr1 is replaced by the current supply transistor Tr2.

Although not shown in the drawings, each of the current supplytransistors Tr1 and Tr2 is provided with a malfunction-preventingresistor connected between the gate terminal and the source terminal.Accordingly, when the on/off command signals SD1 or SD2 is changed tothe low level to turn off the switching element 27 or 28 of the drivecircuit 21 or 22, since the gate-source voltage of the current supplytransistor Tr1 or Tr2 becomes 0 V, the current supply transistor Tr1 orTR2 completely turns off.

Further, in the unlikely case where the output voltage of the voltagestep-up circuit 25 decreases below the current supply performancelowering voltage (decreases to 0 V, for example) when the on/off commandsignal SD1 or SD2 is at the high level, since the gate terminal of thecurrent supply transistor Tr1 or TR2 is applied with a voltage equal tothe battery voltage VB minus the forward voltage Vf (about 0.6 V) of thediode 26, it is possible to turn on the current supply transistor Tr1 orTr2 in a state where a necessary minimum current is passed to the relaycoil 13 a although the current supply performance in this state is lowerthan that in the low current supply performance state. That is, thediode 26 and the switching element 28 are provided to enable thefail-safe operation for each of the drive circuits 21 and 22.

Next, the operation of the voltage variation control section 31 isexplained. The voltage variation control section 31 is configured tovary the source voltages VS1 and VS2 of the current supply transistorsTR1 and Tr2 by varying their gate voltages VG1 and VG2 during thecurrent supply period in which both the on/off command signals SD1 andSD2 outputted from the microcomputer 20 are at the high level. Morespecifically, the voltage variation control section 31 is configured toalternately bring the voltage variation command signals SC1 and SC2respectively supplied to the drive circuits 21 and 22 to the high levelat intervals of a predetermined time Ta for a predetermined time Tbshorter than the time Ta, as shown in FIG. 3. In other words, thevoltage variation control section 31 sets each of the voltage variationcommand signal SC1 and SC2 at the high level during the time Tb atintervals of the time of 2×Ta with a phase difference of the time Tabetween these signals.

Accordingly, the period of the time Tb in which one of the currentsupply transistors Tr1 and Tr2 is in the completely on state, and theother is in the low current supply performance state occurs at intervalsof the time Ta within the current supply period of the relay coil 13 a,and the current supply transistors Tr1 and Tr2 are set to the high levelalternately at intervals of the time Ta. In this embodiment, the periodof the time Tb is a check period for detecting wire breakage of the loadside portion LS1 or LS2 of the current supply wire L1 or L2.

As shown in FIG. 3, in this embodiment, assuming that the batteryvoltage VB is 14 V, when the voltage variation command signal SC1 ischanged to the high level as a result of which the gate voltage VG1 ofthe current supply transistor Tr1 decreases from the completely turn-onvoltage (20 V) to the current supply performance lowering voltage (15V), since the current supply transistor Tr1 turns on in the low currentsupply performance state, the drain-source voltage of the current supplytransistor Tr1 increases from 0.5 V to 1.0 V, and the source voltage ofthe current supply transistor Tr1 decreases from 13.5 V to 13.0 V.

Likewise, when the voltage variation command signal SC2 is changed tothe high level as a result of which the gate voltage VG2 of the currentsupply transistor Tr2 decreases from the completely turn-on voltage (20V) to the current supply performance lowering voltage (15 V), since thecurrent supply transistor Tr2 turns on in the low current supplyperformance state, the drain-source voltage of the current supplytransistor Tr2 increases from 0.5 V to 1.0 V, and the source voltage ofthe current supply transistor Tr2 decreases from 13.5 V to 13.0 V.

At this time, since the source terminals of the current supplytransistors Tr1 and Tr2 are connected to the terminal 117 of the ECU 11,the load voltage (the voltage applied to the relay coil 13 a) which isequal to the voltage of the terminal 17 decreases from 13.5 V to 13.0 Vas shown in FIG. 3.

The voltage variation control section 31 is allowed to operate to setthe voltage variation command signal SC1 or SC1 at the high level by themicrocomputer 20. Next, the operation of the failure detecting section32 is explained.

The failure detecting section 32 is connected to the output terminals(the drain and source terminals) of each of the current supplytransistors TR1 and Tr2, and performs a load side wire breakagedetection process shown in FIG. 4 to detect wire breakage in the loadside portions LS1 and LS2 of the current supply wires L1 and L2.

As shown in FIG. 4, this process begins in step S110 to determinewhether or not a difference between the source voltage VS1 and VS2 ofthe current supply transistors Tr1 and Tr2 exceeds a predeterminedthreshold value. If the determination result in step S110 isaffirmative, the process proceeds to step S120 to output a load sidewire breakage detection signal to the microcomputer 20 assuming that awire breakage has occurred in the load side portion LS1 or LS2.

Incidentally, although the current supply transistors and the currentsupply wires are two in number in this embodiment, they may be three ormore in number. In short, step S120 determines that there is a wirebreakage in one of the current supply wires when a difference in thesource voltage between any one of the current supply transistors and anyother one of the current supply transistors exceeds the threshold value.The failure detecting section 32 may be configured to perform the loadside wire breakage detection process constantly, or only within thecurrent supply period of the relay coil 13 a, or only during the checkperiod within the current supply period. Upon receiving the load sidewire breakage detection signal from the failure detecting section 32,the microcomputer 20 stores a failure code indicating occurrence of afailure identified by the load side wire breakage detection signal in anonvolatile memory, and performs a warning process to inform the vehicledriver of the occurrence of the failure by turning on a warning light orshowing a message corresponding to the detected failure on a display.

The principle of detecting wire breakage in the load side portion LS1 orLS2 is explained in the following. In the normal state where there is nowire breakage, since the source terminals as the load side outputterminals of the current supply transistors Tr1 and Tr2 are connected toeach other through the load side portions LS1 and LS2, the sourcevoltages VS1 and VS2 of the source terminals are always the same witheach other.

If a wire breakage occurs in any one of the load side portions LS1 andLS2, the current supply transistor TRx (x being 1 or 2) connected to theload side portion LSx having the wire breakage is disconnected from thesource terminal of the other current supply transistor and the relaycoil 13 a.

Accordingly, during the check period of the length of the time Tb inwhich the current supply transistor other than the current supplytransistor Trx is turned on in the low current supply performance state,the drain-source voltage of the current supply transistor Trx is at 0.5V as is expected in the completely on period, while the drain-sourcevoltage of the other current supply transistor is at 1.0 V. Accordingly,the source voltage of the current supply transistor Trx becomes thebattery voltage VB minus 0.5 V, while the source voltage of the othercurrent supply transistor becomes the battery voltage VB minus 1.0 V.Therefore, there occurs a difference larger than a certain thresholdvalue between the source voltage VSx of the current supply transistorVSx and the source voltage of the other current supply transistor.

Accordingly, in this embodiment, the threshold value used in step S110is set to a value (0.4 V, for example) which is equal to or slightlysmaller than the difference between 1.0 V and 0.5 V, and it isdetermined that there is a wire breakage in one of the load sideportions LS1 and LS2 if a difference between the source voltages VS1 andVS2 is detected to be larger than the threshold value.

Accordingly, as shown in FIG. 3, if a wire breakage occurs in the loadside portion LS2 of the current supply wire L2 at time t1, and thebattery voltage VB is 14.0 V, when there comes the check period of thelength of the time Tb in which the voltage variation command signal SC1is set at the high level, the voltage variation command signal SC2 isset at the low level so that the current supply transistor TR2 turns onin the completely on state, and the current supply transistor Tr1 turnson in the low current supply performance state, the source voltage VS1of the current supply transistor Tr1 becomes 13.0 V, while the sourcevoltage VS2 of the current supply transistor Tr2 becomes 13.5 V. As aresult, since the difference between the source voltage VS1 and VS2exceeds the threshold value, it is determined that one of the load sideportions LS1 and LS2 is broken.

Incidentally, when the load side portion LS2 of the current supply wireL2 is broken, the current supply transistor Tr1 supplies a current tothe relay coil 13 during the check period in which the voltage variationcommand signal CS1 is at the low level and the voltage variation commandsignal CS2 is at the high level even if the gate voltage VG1 is notdecreased. Accordingly, in this case, although the current supplytransistor Tr2 is not connected to the relay coil 13 a, since the gatevoltage VG2 decreases to 15 V, the source voltage VS2 is loweredcompared to the normal state. Hence, since the difference between thesource voltages VS1 and VS2 does not exceed the threshold value, no wirebreakage is detected.

The failure detecting section 32 includes an on-state monitoring section32 a. The on-state monitoring section 32 a is activated when both theon/off command signals SD1 and SD2 outputted from the microcomputer 20are at the high level to monitor the drain-source voltages of thecurrent supply transistors Tr1 and Tr2. Upon detecting that any one ofthe drain-source voltages of the current supply transistors Tr1 and Tr2exceeds a specific value Vdso set for detecting abnormality, theon-state monitoring section 32 a outputs a circuit abnormality signal tothe microcomputer 20.

The specific value Vdso is set to a value (4 V, for example) higher thanthe drain-source voltage (1 V, for example) when the current supplytransistors Tr1 or Tr2 is turned on in the low current supplyperformance state. The voltage variation control section 31 isconfigured to set a current-supply-period signal outputted to thefailure detecting section 32 to the high level during the current supplyperiod in which both the on/off command signals SD1 and SD2 outputtedfrom the microcomputer 20 are at the high level. The failure detectingsection 32 operates while the current-supply-period signal is at thehigh level. The failure detecting section 32 may be inputted with theon/off command signals SD1 and SD2 outputted from the microcomputer 20instead of the current-supply-period signal.

Next, a voltage variation control inhibition process which themicrocomputer 20 performs in connection with the wire breakage detectionfor the current supply wires L1 and L2 is explained with reference toFIG. 5. The microcomputer 20 performs this voltage variation controlinhibition process at regular time intervals during the current supplyperiod in which the microcomputer 20 sets both the on/off commandsignals SD1 and SD2 at the high level. The microcomputer 20 allows thevoltage variation control section 31 to operate immediately after beingpowered on.

As shown in FIG. 5, the voltage variation control inhibition processbegins in step S210 to determine whether the drain-source voltage of anyone of the current supply transistors Tr1 and Tr2 exceeds the specifiedvalue Vdso based on whether or not the circuit abnormality signal hasbeen outputted from the failure detecting section 32.

If the determination result in step S210 is negative, the processproceeds to step S220. In step S220, it is determined whether or not thefailure detecting section 32 has detected a wire breakage of the currentsupply wire L1 or L2. More specifically, it is determined whether or notthe load side wire breakage detection signal has been outputted from thefailure detecting section 32. If the determination result in step S220is negative, the process proceeds to step S240.

On the other hand, if the determination result in step S210 or step S220is affirmative, the process proceeds to step S230. In step S230, thevoltage variation control section 31 is inhibited from operating toprevent the voltage variation command signals SC1 and SC2 from being setto the high level, and then this process is terminated.

The inhibition to the voltage variation control section 31 continuesafter the present current supply period of the relay coil 13 a ends andthe next current supply period comes. The microcomputer 20 releases theinhibition to the voltage variation control section 31 to allow thevoltage variation control section 31 to operate when the microcomputer20 restarts thereafter, or when the microcomputer 20 receives aninhibition release signal transmitted from outside of the ECU 11.

In step S240, the battery voltage VB received through the terminal 19 isA/D-converted, and it is determined whether or not the battery voltageVB has decreased below a predetermined low voltage detection thresholdVb1. If the determination result in step S240 is negative, the processproceeds to step S250. The low voltage detection threshold Vb1 is set toa value (10 V, for example) lower than the normal range of the value ofthe battery voltage VB.

In step S250, it is determined whether or not at least one of specificelectrical loads (the starter or defogger, for example) which may causethe battery voltage VB to drop below the low voltage detection thresholdVb1 has been powered on or supplied with a current, based on informationshowing control states of the specific electrical loads received fromvehicle-mounted units for controlling theses electrical loads. If thedetermination result in step S250 is negative, the process proceeds tostep S260 to release inhibition made in the later described step S270,and then this process is terminated.

If the determination result in step S240 or step S250 is affirmative,the process proceeds to step S270 assuming that the battery voltage VBis lower than the low voltage detection threshold.

In step S270, the voltage variation control section 31 is inhibited fromoperating, and then this process is terminated. The inhibition to thevoltage variation control section 31, which is released in step S260, isfor inhibiting the voltage variation control section 31 from operatingwhen the determination result in step S240 or S250 is affirmative.

According to the above described process performed by the ECU 11 makesit possible to detect wire breakage in the load side portions LS1 andLS2 of the current supply wires L1 and L2 respectively connected withthe current supply transistors Tr1 and Tr2. Further, since the relaycoil 13 a is supplied with a current through all the current supplytransistors Tr1 and Tr2 during the current supply period of the relaycoil 13 a, it can be prevented that the current supply transistors Tr1and Tr2 are overloaded, and that current supply to the relay coil 13 ais interrupted when one of the current supply wires L1 and L2 is broken.

Incidentally, the check period of the length of the time Tb in which oneof the voltage variation command signals SC1 and SC2 is at the highlevel may be generated continuously and successively. However,generating the check period intermittently at regular time intervals ofthe time Ta is advantageous in view of reduction of power loss in thecurrent supply transistors Tr1 and Tr2.

In this embodiment, when the drain-source voltage of any one of thecurrent supply transistors Tr1 and Tr2 exceeds the specific value Vdsoduring the current supply period of the relay coil 13 a, it is detectedin steps S210 and S230 shown in FIG. 5, and as a result the voltagevariation control section 31 is inhibited from operating thereafter.

Accordingly, if there occurs a circuit abnormality in which the outputvoltage of the voltage step-up circuit 25 decreases below the currentsupply performance lowering voltage when the voltage variation commandsignal SC1 is set to the high level, due to abnormality in the voltagecontrol section 25 b of the voltage step-up circuit 25 of one or both ofthe drive circuits 21 and 22 (it is assumed that the abnormality is inonly the drive circuit 21 in the following description), and as aresult, the drain-source voltage of the current supply transistor Tr1exceeds the specified value Vdso, the voltage variation command signalsSC1 and SC2 are inhibited from being set to the high level thereafter.Accordingly, according to the above embodiment, it is possible toprevent the power loss of the current supply transistor Tr1 frombecoming excessively large, and to prevent the current supplied to therelay coil 13 a from being reduced. The above explanation applies alsoto the drive circuit 22 and the current supply transistor Tr2.

The on-state monitoring section 32 a of the failure detecting section 32may be configured to monitor the drain-source voltage of only one of thecurrent supply transistors Tr1 and Tr2. However, in this embodiment, theon-state monitoring section 32 a of the failure detecting section 32 isconfigured to monitor the drain-source voltages of both the currentsupply transistors Tr1 and Tr2 to increase the reliability of thefailure detection. The on-state monitoring section 32 a may beconfigured to operate to monitor the drain-source voltages of thecurrent supply transistors Tr1 and Tr2 only during the check period inwhich one of the voltage variation command signals SC1 and SC2 is set tothe high level within the current supply period of the relay coil 13 a.

According to this embodiment, since the voltage variation controlsection 32 is inhibited from operating after any one of the currentsupply wires L1 and L2 is detected to be broken by the failure detectingsection 32, it is possible to prevent the current supplied to the relaycoil 13 a from being reduced because the current supply transistorconnected to the normal one of the current supply wires is not set tothe low current supply performance state.

Further, according to this embodiment, it is possible to turn on thecurrent supply transistors Tr1 and Tr2 in a state enabling to supply acurrent to the coil 13 a necessary to turn on the relay 13, even if thedrive voltage applied to the gate terminals of the current supplytransistors Tr1 and Tr2 is decreased below a value minimally necessaryto turn on the current supply transistors Tr1 and Tr2 due to failure ofthe voltage step-up circuit 25 or the switching element 27 of the drivecircuit 21 or 22, because of the provision the diode 26 and theswitching element 28.

In addition, according to this embodiment, it is possible to prevent thecurrent supplied to the relay coil 13 a from being excessively reducedwhen the battery voltage VB is low, causing the voltage variationcommand signals SC1 and SC2 to be at the high level, because step S270inhibits the voltage variation control section 31 from operating whenthe battery voltage VB is detected to be lower than the low voltagedetection threshold Vb1 in step S240 or S250. One of steps S240 and S250may be omitted.

In this embodiment, the relay coil 13 a is an object to be supplied witha current, however, the relay 13 itself can be assumed as an object tobe driven.

Next, various modifications of the above described embodiment aredescribed. The above embodiment may be modified such that the voltagevariation command signals SC1 and SC2 are inputted also to the failuredetecting section 32 to enable the failure detecting section 32 todetermine that it is during the check period at present, and which ofthe current supply transistors is in the completely on state during thischeck period. This is because, if any one of the voltage variationsignals SC1 and SC2 is at the high level, it can be determined that itis during the check period at present, and the current supply transistorcorresponding to one of the voltage variation signals SC1 and SC2 whichis at the low level is turned on completely, and the other currentsupply transistor is in the low current supply performance state.

In this modification, the failure detecting section 32 performs the loadside wire breakage detecting process shown in FIG. 4 only during thecheck period. Upon detecting that the difference between the sourcevoltages VS1 and VS2 exceeds the threshold value, the failure detectingsection 32 determines that the load side portion of the current supplywire to which the current supply transistor set in the completely onstate is connected is broken, and outputs a load side wire breakagedetection signal added with information to identify the broken currentsupply wire to the microcomputer 20.

The above modification makes it possible that the microcomputer 20identifies which of the load side portions of the current supply wiresL1 and L2 is broken. For example, in the case shown in FIG. 3, if theload side portion LS2 is broken at time t1, there is determined, duringthe check period thereafter in which the voltage variation commandsignal SC1 is set to the high level and the voltage variation commandsignal SC2 is set to the low level, that the load side portion LS2 ofthe current supply wire L2 is broken, and the load side wire breakagedetection signal indicating that effect is outputted from the failuredetecting section 32 to the microcomputer 20.

Further, the above embodiment may be modified such that, with thedecrease of the battery voltage VB, the degree of lowering of thecurrent supply performance of the current supply transistors Tr1 and Tr2during the check period is decreased, the check period of the length oftime Tb is shortened, or the generation interval of the time Ta of thecheck period is lengthened, in order to prevent the current supplied tothe relay coil 13 a from being reduced.

Further, the above embodiment may be modified such that the circuitabnormality signal and the load side wire breakage detection signaloutputted from the failure detecting section 32 are inputted to thevoltage variation control section 31, and the failure detecting section32 stops operation when any one of the circuit abnormality signal andthe load side wire breakage detection signal is received. In thismodification, steps S210 to S230 in the process shown in FIG. 5 may beomitted.

Further, steps S240 to S270 may be performed by a circuit other than themicrocomputer 20.

Second Embodiment

Next, a second embodiment of the invention is described.

The ECU 11 of the second embodiment is different from that of the firstembodiment in the following points (1) and (2).

(1) The voltage variation control section 31 sets the voltage variationcommand signals SC1 and SC2 to the high or low level not only in thepattern shown in FIG. 3, but also in the pattern shown in FIG. 6.

In the second embodiment, after a first check period in which thevoltage variation command signals SC1 and SC2 are set to the high levelalternately during the predetermined time Tb at the time intervals ofthe time Ta as shown in FIG. 3 is generated 2N times (N being an integerlarger than or equal to 1), that is after each of the voltage variationcommand signals SC1 and SC2 is changed to the high level N times, asecond check period in which both the voltage variation command signalsSC1 and SC2 are set to the high level at the same time during thepredetermined time Tb at regular time intervals of the time Ta isgenerated M times (M being an integer larger than or equal to 1). The2×N times generations of the first check period and the M timesgenerations of the second check period are repeated during the currentsupply period.

FIG. 6 shows the case in which only the second check period isgenerated. However, it is possible to change the voltage variationcommand signals SC1 and SC2 between the high level and the low levelindependently in the pattern shown in FIG. 7, for example. FIG. 7 showsan example where the N and M are 1. Accordingly, in the example shown inFIG. 7, a check period in which only the voltage variation commandsignal SC1 is set to the high level, a check period in which only thevoltage variation command signal SC2 is set to the high level, and acheck period in which both the voltage variation command signal SC1 andSC2 are set to the high level are included in each cycle of the lengthof 3×Ta.

In the second embodiment, the check period in which both the voltagevariation command signal SC1 and SC2 are set to the high level is aperiod for detecting wire breakage in the opposite load side portionsLD1 and LD2, and is different in kind from the check period in which oneof the voltage variation command signals SC1 and SC2 is set to the highlevel. Hereinafter, this period is referred to as “different kindperiod”.

(2) The voltage variation command signals SC1 and SC2 outputted from thevoltage variation control section 31 are inputted also to the failuredetecting section 32. The failure detecting section 32 performs anopposite load side wire breakage detection process shown in FIG. 8 todetect wire breakage of the opposite load side portions LD1 and LD2 ofthe current supply wires L1 and L2 during the different kind checkperiod in which both the voltage variation command signals SC1 and SC2are set to the high level.

As shown in FIG. 8, the opposite load side wire breakage detectionprocess begins in step S310 to determine whether or not each of thedrain-source voltages of the current supply transistors Tr1 and Tr2 islower than a predetermined threshold value. If the determination resultin step S310 is affirmative, the process proceeds to step S320 to outputan opposite load side wire breakage detection signal indicating that oneof the opposite load side portions LD1 and LD2, which is connected withthe current supply transistor whose drain-voltage source is detected tobe lower than the threshold value, to the microcomputer 20.

In this embodiment, since the drain-source voltages of the currentsupply transistors Tr1 and Tr2 are higher than 1 V when the voltagevariation command signals SC1 and SC2 are at the high level, thethreshold value is set lower than 1 V. Upon receiving the opposite loadside wire breakage detection signal from the failure detecting section32, the microcomputer 20 stores a failure code indicating occurrence ofa failure identified by the opposite load side wire breakage detectionsignal in the nonvolatile memory, and performs a warning process toinform the vehicle driver of the occurrence of the failure by turning ona warning light or showing a message corresponding to the detectedfailure on a display.

Next, the principle of detecting wire breakage of the opposite load sideportions LD1 and LD2 is explained. In the normal state where there is nowire breakage (before time t2 in FIG. 6), the drain-source voltages ofthe current supply transistors Tr1 and Tr2 are at 1 V during thedifferent kind check period in which both the voltage variation signalsSC1 and SC2 are set to the high level. In FIG. 6, the description“VS1−VD1” means the source voltage VS1 minus the drain voltage VD1 ofthe current supply transistor Tr1, which is the sign-inverted version ofthe drain-source voltage of the current supply transistor Tr1. Likewise,the description “VS1−VD1” means the sign-inverted version of thedrain-source voltage of the current supply transistor Tr2.

If any one of the opposite load side portions LD1 and LD2 is broken,since no current flows through the current supply transistor Trx (xbeing 1 or 2) connected to the broken opposite load side portion LDx,the relay coil 13 a is supplied with a current only through the othercurrent supply transistor. As a result, the drain-source voltage of thecurrent supply transistor connected to the opposite load side portionwhich is not broken becomes higher than or equal to 1 V, while thedrain-source voltage of the current supply transistor Trx connected tothe opposite load side portion LDx which is broken becomes lower than 1V reliably, because no current flows through the current supplytransistor Trx.

Accordingly, in this embodiment, the threshold value used in step S310shown in FIG. 8 is set lower than 1 V (0.7 V, for example) to determinethat the opposite load side portion of the current supply wire connectedwith the current supply transistor whose drain-source voltage is lowerthan the threshold value during the different kind check period isbroken.

For example, if the opposite load side portion LD2 of the current supplywire L2 is broken at time t2, when there comes the different kind checkperiod of the length of the time Tb in which both the voltage variationcommand signals SC1 and SC2 are set at the high level, the drain-sourcevoltage of the current supply transistor Tr1 becomes 1 V, while thedrain-source voltage of the current supply transistor Tr2 becomes 0.5 Vlower than the threshold value. Accordingly, the opposite load sideportion LD2 connected with the current supply transistor Tr2 isdetermined to be broken.

According to the second embodiment, also wire breakage of the oppositeload side portions LD1 and LD2 of the current supply wires L1 and L2 canbe detected. In the second embodiment, since the different kind checkperiod is generated intermittently, the wire breakage detection can beperformed for the opposite load side portion LD1 and the opposite loadside portion LD2 intermittently and repeatedly.

In this embodiment, it is determined whether or not the opposite loadside wire breakage signal has been outputted from the failure detectingsection 32 in step S220 of the voltage variation control inhibitionprocess shown in FIG. 5, and if the determination result in step S220 isaffirmative, the process proceeds to step S230 to inhibit the voltagevariation control section 31 from operating thereafter. Accordingly,according to this embodiment, it is possible to prevent the currentsupplied to the relay coil 13 a from being reduced also in a case whereany one of the opposite load side portions LD1 and LD2 of the currentsupply wires L1 and L2 is broken, because the current supply transistorconnected to the current supply wire with no wire breakage is not set tothe low current supply performance state in this case. It is a matter ofcourse that various modifications can be made to the above embodimentsas described below.

The microcomputer 20 may be configured to output the on/off commandsignals SD1 and SD2 from the same terminal instead of from the separatetwo terminals. In this modification, the common on/off command signal isinputted to the drive circuits 21 and 22, and the voltage variationcontrol section 31.

The current supply wires and the current supply transistors may be threeor more in number. The current supply transistors may be P-channelMOSFETs. The current supply transistors may be IGBTs or bipolartransistors. In a case where bipolar transistors, which arecurrent-driven type transistors, are used as the current supplytransistors, the low current supply performance state can be achieved byreducing a current supplied to the base terminal as a control terminalof each current supply transistor.

The relay coil 13 a may be a low side driven relay coil. In this case,one end of the relay coil 13 a is connected to the positive terminal ofthe battery 15, the other end of the relay coil 13 a is connected to theterminal 19 of the ECU 11, and the terminal 17 of the ECU 11 isconnected to the ground line. Accordingly, the portions designated byLD1 and LD2 of the current supply wires L1 and L2 in FIG. 1 correspondto the load side portions, and the portions designated by LS1 and LS2correspond to the opposite load side portions.

In the above embodiments, the relay coil 13 a of the relay 13 is theelectrical load as an object to be supplied with a current. However, theelectrical load as an object to be supplied with a current is notlimited to the relay coil 13 a. For example, it may be an actuator suchas an electrical motor whose output power depends on a current supplied.In this case, in addition to, or instead of steps S240 and S250, a stepfor determining whether or not a current supplied to the actuator shouldbe increased as much as possible is provided in the process shown inFIG. 5, and if the determination result in this step is affirmative, theprocess proceeds to step S270.

The above explained preferred embodiments are exemplary of the inventionof the present application which is described solely by the claimsappended below. It should be understood that modifications of thepreferred embodiments may be made as would occur to one of skill in theart.

What is claimed is:
 1. An electrical load driving apparatus comprising:a plurality of current supply wires connected in parallel with oneanother, each of the current supply wires being connected to one of ahigh voltage terminal and a low voltage terminal of a power source atone end thereof, and being connected to one end of an electrical load atthe other end thereof, the other end of the electrical load beingelectrically connected with the other of the high voltage terminal andthe low voltage terminal of the power source; a plurality of currentsupply transistors having one control terminal and two output terminals,each of the current supply transistors being interposed in acorresponding one of the current supply wires at the two outputterminals thereof to supply a current to the electrical load when beingturned on during a current supply period in which the electrical load isconfigured to be supplied with the current continuously; a check periodgenerating section that successively generates a first check periodwithin the current supply period, a specific one of the current supplytransistors being turned on in a completely turn-on state where avoltage difference between the two output terminals thereof is lowerthan or equal to a predetermined value so that the specific currentsupply transistor is turned on completely, the current supplytransistors other than the specific current supply transistor beingturned on in a low current supply performance state where a voltagedifference between the two output terminals thereof is higher than thepredetermined value so that the current supply transistors other thanthe specific current supply transistor are turned on incompletely, thespecific current supply transistor being selected from among all of thecurrent supply transistors in sequence within the current supply period;and a wire breakage determining means configured to determine, upondetecting that a voltage variation in a voltage of one of the two outputterminals, which is located on the side near the electrical load withrespect to the current supply transistors and between any one of thecurrent supply transistors and any other one of the current supplytransistors, exceeds a predetermined threshold, that a wire breakage ispresent in a portion of one of the current supply wires on the side nearthe electrical load with respect to the current supply transistors. 2.The electrical load driving apparatus according to claim 1, wherein thecheck period generating section generates the first check periodintermittently.
 3. The electrical load driving apparatus according toclaim 1, wherein the wire breakage determining means is activated duringeach first check period, and configured to determine, upon detectingthat the voltage variation exceeds the predetermined threshold, that awire breakage is present in a portion of one of the current supply wireswhich has been selected as the specific current supply transistor duringthe first check period on the side near the electrical load.
 4. Theelectrical load driving apparatus according to claim 1, furthercomprising an abnormality handling means configured to monitor thevoltage difference between the two output terminals for at least one ofthe current supply transistors during the current supply period, andinhibits the check period generating section from operating upondetecting that the voltage difference exceeds an abnormality detectionthreshold.
 5. The electrical load driving apparatus according to claim1, further comprising a check ending means configured to inhibit thecheck period generating section from operating when the wire breakagedetermining means determines that a wire breakage is present.
 6. Theelectrical load driving apparatus according to claim 1, wherein thecurrent supply transistors are voltage-driven type transistors, theelectrical load driving apparatus further comprises a drive meansconfigured to apply a drive voltage to the control terminals of thecurrent supply transistors to turn on the current supply transistorsduring the current supply period, the check period generating means isconfigured to adjust the drive voltage applied to the control terminalof the current supply transistor to be turned on in the low currentsupply performance state so that the current supply transistor is turnedon incompletely, and the electrical load driving apparatus furthercomprises an auxiliary voltage supply means for applying an auxiliarydrive voltage to the control terminals of the current supply transistorsto turn on the current supply transistors in a state where their currentsupply performance is lower than that in the lower current supplyperformance state.
 7. The electrical load driving apparatus according toclaim 1, further comprising a check inhibition means configured toinhibit the check period generating means from operating upon detectingthat the electrical load is in a specific condition.
 8. The electricalload driving apparatus according to claim 7, wherein the specificcondition is that an output voltage of the power source is lower than apredetermined voltage.
 9. The electrical load driving apparatusaccording to claim 1, wherein the check period generating means isconfigured to generate, in addition to the first check period, a secondcheck period in which all the current supply transistors are turned onat the same time in the low current supply performance state within thecurrent supply period, and the electrical load driving apparatus furthercomprises an opposite load side wire breakage determining meansconfigured to monitor the voltage difference between the two outputterminals for each of the current supply transistors during the secondcheck period, and determines, upon detecting that the voltage differencebetween the two output terminals of any one of the current supplytransistors is smaller than a detection threshold smaller than thepredetermined value, that the current supply wire interposed by thedetected current supply transistor is broken at a portion thereof on theopposite side of the detected current supply transistor with respect tothe electrical load.
 10. The electrical load driving apparatus accordingto claim 9, wherein the check period generating means generates thesecond check period intermittently within the current supply period.